Clock circuitry

ABSTRACT

A circuit comprising: clock circuitry for supplying a first faster clock signal to a first circuit portion and a second slower clock signal to a second circuit portion, and varying the relative frequency of the first and second clock signals. Synchronisation logic generates pulses which indicate when to transfer data between the first and second circuit portions. The clock circuitry generates a first control signal at a predetermined time in each cycle of the first clock signal prior to a predetermined edge, and a second control signal at a predetermined time in each cycle of the second clock signal prior to a predetermined edge. A change in the relative frequency is conditional on a coincidence of the first and second control signals. The synchronisation generates the pulses such that there is at least one cycle of the first clock signal between those pulses, and such that there is only one of those pulses per cycle of the second clock signal.

FIELD OF THE INVENTION

The present invention relates to coordinating the transfer of databetween variable clock domains.

BACKGROUND

Different portions of the same overall circuit may be required tooperate at different clock speeds, and furthermore one or more of thoseclock speeds may be variable. Each portion operating at a given clockspeed defines a respective clock domain. For example, FIG. 1 showsschematically an integrated circuit comprising a first circuit portion Aclocked by a first clock signal clk-A defining a first clock domain A,and a second circuit portion B clocked by a second clock signal clk-Bdefining a second clock domain B. In this example, the first circuit Ais to transfer data to the second circuit portion B, and furthermore thefrequency of each of the first and second clock signals clk-A and clk-Bis variable.

However, there are two issues with this: firstly, ensuring the data ispassed from one clock domain to another in a synchronised manner; andsecondly, ensuring that the transfer remains synchronised even when oneor both of the clocks changes speed.

There are a number of standard mechanisms for crossing clock-domainboundaries between components of a silicon chip or other circuit.However, whilst these can provide sufficient bandwidth, they suffer fromhaving significant latency due to the need to resolve metastability andfor most high-bandwidth schemes to exchange handshake control signals inboth directions across the interface. For high frequency systems,special high-gain flip-flops may also be required in order to provide asufficiently high probability of resolving meta-stability.

Similarly, clock-frequency changes typically require clocks to bestopped whilst the dividers change frequency so that logic is notsubject to glitches (which violate timing and cause functional errors).They also may require that traffic across the interface is stopped sothat the interface is in a known “safe” state and accesses cannot belost or corrupted.

It would be advantageous to provide an improved way of passing databetween variable clock domains.

SUMMARY

According to one aspect of the present invention, there is provided acircuit comprising: clock circuitry comprising clock generating meansarranged to supply a first clock signal having a first faster frequencyto a first circuit portion and a second clock signal having a secondslower frequency to a second circuit portion, the clock generating meansbeing operable to vary the relative frequency of the first and secondclock signals; synchronisation logic arranged to generate pulses basedon the first and second clock signals, each pulse indicating when totransfer data between the first circuit portion and the second circuitportion; gating means arranged to produce a gated clock signal by gatingthe first clock signal, the gating means being open when said pulses areasserted; and transfer means arranged to clock data between the firstcircuit portion and the second circuit portion when clocked by the gatedclock signal; wherein the clock circuitry comprises control logicconfigured to generate a first control signal at a predetermined time ineach cycle of the first clock signal prior to a predetermined edge ofthe first clock signal, and to generate a second control signal at apredetermined time in each cycle of the second clock signal prior to apredetermined edge of the second clock signal, the clock generatingmeans being configured such that a change in said relative frequency isconditional on a coincidence of the first and second control signals;and the synchronisation logic is configured to generate said pulses suchthat there is at least one cycle of the first clock signal between saidpulses, and such that there is only one of said pulses per cycle of thesecond clock signal.

This combination of clock circuitry and synchronisation logicadvantageously provides low-latency clock domain crossing that safelysupports dynamic clock frequency changes without requiring the clocks tostop whilst changes are in progress. Further, this circuit canadvantageously be implemented using only a small amount of logic.

According to another aspect of the present invention, there is providedmethod comprising: supplying a first clock signal having a first fasterfrequency to a first circuit portion; supplying a second clock signalhaving a second slower frequency to a second circuit portion; generatinga first control signal at a predetermined time in each cycle of thefirst clock signal prior to a predetermined edge of the first clocksignal; generating a second control signal at a predetermined time ineach cycle of the second clock signal prior to a predetermined edge ofthe second clock signal; varying the relative frequency of the first andsecond clock signals on the condition of detecting a coincidence of thefirst and second control signals; generating pulses based on the firstand second clock signals to indicate when to transfer data between thefirst circuit portion and the second circuit portion, such that there isat least one cycle of the first clock signal between said pulses, andsuch that there is only one pulse per cycle of the second clock signal;producing a gated clock signal by gating the first clock signal so as topass it when said pulses are asserted; and transferring data between thefirst circuit portion and the second circuit portion, the transfer beingclocked by the gated clock signal.

According to another aspect of the present invention, there is provideda circuit comprising: clock circuitry comprising clock generating meansarranged to supply a first clock signal having a first faster frequencyto a first circuit portion and a second clock signal having a secondslower frequency to a second circuit portion, the clock generating meansbeing operable to select between a plurality of predetermined ratiosbetween the first and second clock frequencies; synchronisation logicfor generating pulses based on the first and second clock signals, eachpulse indicating when to transfer data between the first circuit portionand the second circuit portion; gating means arranged to produce a gatedclock signal by gating the first clock signal, the gating means beingopen when said pulses are asserted; and transfer means arranged totransfer data between the first circuit portion and the second circuitportion when clocked by the gated clock signal; wherein thesynchronisation logic comprises a chain of at least two flip-flopsarranged to shift through the second clock signal when clocked by thefirst clock signal, and combinational logic arranged to generate saidpulses in dependence on a combination of outputs from each of saidflip-flops; and the combinational logic is arranged to receive a ratioindication signal indicative of the ratio between the first and secondfrequencies, and to generate said pulses using said ratio indicationsignal such that regardless of the selected ratio: there is at least onecycle of the first clock signal between said pulses, and there is onlyone of said pulses per cycle of the second clock signal.

According to another aspect of the present invention, there is provideda method comprising: supplying a first clock signal having a firstfaster frequency to a first circuit portion; supplying a second clocksignal having a second slower frequency to a second circuit portion;selecting the relative frequency between the first and second clocksignals from a plurality of predetermined ratios; shifting the secondclock signal through a chain of at least two flip-flops, the shiftingbeing clocked by the first clock signal; receiving a ratio indicationsignal indicative of the ratio between the first and second frequencies;generating pulses which indicate when to transfer data between the firstcircuit portion and the second circuit portion, by using a combinationof outputs from each of said flip-flops and said ratio indication signalsuch that, regardless of the selected ratio, there is at least one cycleof the first clock signal between said pulses, and there is only onepulse per cycle of the second clock signal; producing a gated clocksignal by gating the first clock signal so as to pass it when the pulsesare asserted; and transferring data between the first circuit portionand the second circuit portion, the transfer being clocked by gatedclock signal.

For a better understanding of the present invention and to show how itmay be carried into effect, reference will now be made by way of exampleto the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a schematic block diagram of two clock domains,

FIG. 2 is a schematic block diagram of a clock gearbox circuit,

FIG. 3 is a timing diagram showing coordination of frequency dividers,

FIG. 4 is a timing diagram showing generation of synchronisation pulses,

FIG. 5 is another timing diagram showing generation of synchronisationpulses,

FIG. 6 is a circuit diagram of a transmit synchronisation generator,

FIG. 7 is a circuit diagram of a receive synchronisation generator,

FIG. 8 is a circuit diagram of a transmit and receive synchronisationgenerator,

FIG. 9 is another timing diagram of the generation of synchronisationpulses,

FIG. 10 a is another timing diagram of the generation of synchronisationpulses,

FIG. 10 b is another timing diagram of the generation of synchronisationpulses,

FIG. 11 is a timing diagram of set-up and hold times, and

FIG. 12 is a timing diagram of domain handovers.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS

FIG. 2 shows circuitry referred to herein as a “clock gearbox”. Where aplurality of separate clocks are generated from a single clock source,and there is a requirement to hand-over between the domains, then thereis scope to improve upon the problems in the prior art discussed above.In the preferred embodiments, the clock gearbox mechanism provides thefollowing advantages:

-   -   low-latency clock-domain crossing in both directions between        fast and slow core clock domains;    -   on-the-fly, dynamic clock frequency switching, allowing greater        opportunities to save power);    -   the clock switching does not require intervention from software        (other than to request the change);    -   simpler logic and reduced flip-flop count at the crossing;    -   the potential to place logic on the path between flops in each        clock domain (which is not normally possible due to the risk of        capturing logic glitches in the destination domain) subject to        normal timing analysis.

The clock gear box consists of two main components (each of which may beinstanced multiple times) to provide the advantages above:

-   -   clock dividers 6 that co-ordinate frequency changes to maintain        certain properties on the clocks, and    -   Synchronisation logic 10 to generate “sync-enables” in the fast        domain which signify when it is safe to sample slow-domain data        and safe to update data to send to the slow-domain.

Practical systems are also likely to require FIFOs 20 in the fast domainto buffer incoming data to transfer to the slow domain.

The circuitry of FIG. 2 is now described in more detail. In thisexample, although the frequencies of both clock signals clk-A and clk-Bare variable, the frequency of the first clock signal clk-A is alwaysgreater (faster) than the frequency of the second clock signal clk-B.

The clock gearbox comprises a first clock divider 6 a and a second clockdivider 6 b. Each divider 6 has a clock input (clk-in), a dividercontrol input (div-ctrl), a load control input (load-ctrl), a clockoutput (clk-out) and a load enable output (load-enable). The clockgearbox also comprises a first divider control register 4 a, a seconddivider control register 4 b, and an AND gate 8.

The clock input (clk-in) of each divider 6 a and 6 b is connected toreceive a source clock signal from a clock source in the form ofphase-locked loop (PLL) 2. The clock input of each divider controlflip-flop is also connected to receive the source clock signal from thePLL 2. The signal input of the first divider control register 4 a isconnected to receive a first divider control signal (fast domain dividerctrl) and the signal input of the second divider control register 4 b isconnected to receive a second divider control signal (slow domaindivider ctrl), each of which signals may be generated by software. Theoutput of the first divider control register 4 a is connected to thedivider control input (div-ctrl) of the first divider 6 a and the outputof the second divider control register 4 b is connected to the dividercontrol input (div-ctrl) of the second divider 6 b. The load enableoutput (load-enable) of each divider 6 a and 6 b is connected to arespective input of the AND gate 8, and the output of the AND gate 8 isconnected to the load control input (load-ctrl) of each divider 6 a and6 b.

The clock gearbox further comprises a synchronisation generator 10, atransmit clock gate 12, a receive clock gate 16, a first transmitregister 14 a, a second transmit register 14 b, a first receive register18 a, a second receive register 18 b, and a first-in-first-out (FIFO)buffer 20. The synchronisation generator 10 has a first clock input(fast-clk), a second clock input (slow-clk), a transmit synchronisationoutput (tx-sync) and a receive synchronisation output (rx-sync).

The clock output (clk-out) of the first divider 6 a is connected to thefirst clock input (fast-clk) of the synchronisation generator 10, theclock input of the transmit clock gate 12, the clock input of thereceive clock gate 16, a clock input of the FIFO buffer 20, and one ormore clock inputs of the first circuit portion A (not shown). Thetransmit synchronisation output (tx-sync) of the synchronisationgenerator 10 is connected to the enable input of the transmit clock gate12, and the receive synchronisation output (rx-sync) of thesynchronisation generator 10 is connected to the enable input of thereceive clock gate 16. The output of the transmit clock gate 12 isconnected to the clock input of the first transmit register 14 a, andthe output of the receive clock gate 16 is connected to the clock inputof the first receive register 18 a. The clock output (clk-out) of thesecond divider 6 b is connected to the second clock input (slow-clk) ofthe synchronisation generator 10, the clock input of the second transmitregister 14 b, the clock input of the second receive register 18 b, andone or more clock inputs of the second circuit portion B (not shown).

The FIFO buffer 20 has an input connected to receive data from the firstcircuit portion A. The data input of the first transmit register 14 a isconnected to the output of the FIFO buffer 20. The output of the firsttransmit register 14 a is connected to the data input of the secondtransmit register 14 b. The output of the second transmit register 14 bis connected to supply data to the second circuit portion B. The datainput of the second receive register 18 b is connected to receive datafrom the second circuit portion B. The output of the second receiveregister 18 b is connected to the data input of the first receiveregister 18 a. The output of the first receive register 18 a isconnected to supply data to the first circuit portion A.

In operation, the first divider 6 a outputs a first clock signal (clk-A)from its respective clock output (clk-out), which it generates bydividing the source clock signal received at its clock input (clk-in) bya first factor. Similarly, the second divider 6 b outputs a second clocksignal (clk-B) from its respective clock output (clk-out), which itgenerates by dividing the source clock signal received at its clockinput (clk-in) by a second factor.

All the circuitry clocked by the first clock signal clk-A is said to bein the first clock domain. This includes the first circuit portion A,the synchronisation generator 10, the first transmit register 14 a, thefirst receive register 18 a, the FIFO buffer 20, and indirectly thetransmit clock gate 12 and the receive clock gate 16. All the circuitryclocked by the second clock signal is said to be in the second clockdomain. This includes the second circuit portion B, the second transmitregister 14 b, and the second receive register 18 b.

Each of the divider control registers 4 a and 4 b holds a respectivenumber to control the divide ratio in the dividers 6 a and 6 brespectively. This number is the preferably the divide ratio (i.e.division factor) itself, but it could be encoded if a different dividerarchitecture is used. The number is preferably multi-bit, but could be asingle bit for simpler systems. The first division factor is provided bythe first divider control signal (fast domain divider ctrl), which isclocked into the first divider control register 4 a using the PLL sourceclock signal. Similarly, the second division factor is provided by thesecond divider control signal (slow divider control), which is clockedinto the second divider control register 4 b using the PLL source clocksignal

The first divider 6 a is arranged to take its respective first divisionfactor from the first divider control register 4 a into its dividercontrol input (div-ctrl). Similarly, the second divider 6 b is arrangedto take its respective second division factor into its divider controlinput (div-ctrl). Thus the dividers 6 a and 6 b allow the first andsecond clock frequencies to be varied.

Each divider 6 a and 6 b also outputs a respective load enable signalfrom its respective load enable output (load-enable). These are fed backthrough the AND gate 8 to the load control inputs (load-ctrl). Eachdivider is configured to only respond to the value in the respectivedivider control register to allow a variation in clock frequency on thecondition of receiving a signal at its respective load control input(load-ctrl). Thus the AND gate 8 ensures that each divider 6 a and 6 bcan only change clock frequency on the condition that both dividers 6 aand 6 b output a load enable signal from their respective load enableoutputs (load-enable). That is, the frequencies can only change when theload enable signals of the two dividers 6 a and 6 b are coincident intime. The generation of the load enable signals by the dividers 6 a and6 b is discussed later in relation to FIG. 3.

The synchronisation generator 10 produces pulses from the transmit andreceive synchronisation outputs (tx-sync and rx-sync) to indicate onwhich clock cycles of the fast-domain (A) it is safe to send data to theslow domain (B) and to receive data from the slow domain (B)respectively. The generation of these pulses is discussed later inrelation to FIGS. 4 to 10 b.

The pulses from the synchronisation generator are used to gate the first(faster) clock signal clk-A separately through two branches. So thefirst transmit clock gate 12 is used to gate the first clock signalclk-A in dependence on the transmit pulses from the transmitsynchronisation output (tx-sync) to produce a transmit clock signal(tx-clk), and the receive clock gate 16 is used to separately gate thefirst clock signal clk-A in dependence on the receive pulses from thereceive synchronisation output (rx-sync) to produce a receive clocksignal (rx-clk). That is, the transmit and receive clock signals (tx-clkand rx-clk) are gated versions of the first (faster) clock signal clk-Agated in dependence on the transmit and receive pulses from thesynchronisation generator 10 respectively.

The transmit clock signal (tx-clk) is used to clock transmitted datafrom the first circuit portion A into the first transmit register 14 a,via the FIFO buffer 20. The transmitted data is then clocked from thefirst transmit register 14 a into the second transmit register 14 b inthe second (slower) domain B in dependence on the second clock signalclk-B, thus making that data available to the second circuit portion B.

Received data is clocked from the second circuit portion B into thesecond receive register 18 b in dependence on the second clock signalclk-A. The receive clock signal (rx-clk) is then used to clock thereceived data from the second receive register 18 b into the firstreceive flip-flop 18 a in the first (faster) domain, thus making itavailable to the first circuit portion B.

The transmit and receive registers 14 a, 14 b, 18 a and 18 b arepreferably each capable of holding a large number of bits for all thedata crossing the clock-domain boundary. Preferably, this may be of theorder of hundreds of bits in total.

In order to guarantee that the synchronisation pulses (tx-sync andrx-sync) can be successfully generated and that the divider frequenciescan be changed without requiring that the data-flows and clocks arestopped, then the dividers 6 a and 6 b preferably have the followingproperties.

-   -   Frequency changes must only occur when all clocks have        coincident rising edges. This allows the synchronisation signals        syncs to be generated for widest range of clk-A:clk-B frequency        ratios. It also ensures a minimum of two fast cycles per slow        cycle is guaranteed when frequencies change.    -   Clock cycles must never be truncated. This ensures clock        glitches can never occur so clocks do not need to be stopped        when changing frequency.

An example timing diagram showing the coordination of frequency changesusing the clock dividers 6 a and 6 b and AND gate 8 is given in FIG. 3.

As mentioned, the clock dividers 6 a and 6 b provide clock division froma shared source clock 2. Further to this, they have a load control input(load-ctrl) which blocks updating to a new divide ratio, and a loadenable output (load-enable) which signifies when they are about to emita rising edge on the divided clock (clk-A or clk-B respectively). Thatis, the load enable output (load-enable) of each divider 6 a and 6 bgenerates a signal (in this case signalled by a logic-high) at apredetermined point in time in each cycle prior to a predetermined edge(in this case a rising edge). In this way, the AND of all load-enableoutputs (load-enable) can be used to synchronise all relevant clockdividers 6 to update to new frequencies and maintain the relationshipsdescribed above. So the dividers 6 can only update their divide ratioswhen both (or more generally all) dividers 6 are about to issue a risingedge, and thus changes in clock frequency are synchronised.

In FIG. 3, at time (a) new divide ratios are presented to dividers. Attime (b), the update to new ratios is held off. At time (c), bothdividers 6 a and 6 b flag an impending rising edge and so latch the newcontrols. At time (d), two pipeline stages later, the new clocks appearat the divider outputs (although note that other divider designs mayhave different pipeline lengths).

Note also, it is important that the load-enable output (load-enable)generates the load-enable signal at the same number of input PLL clockcycles before an output rising edge as the depth of the dividerpipeline.

Turning now to the operation of the synchronisation generator 10, asmentioned this produces the pulses used to select fast-domain cycles onwhich it is safe to either send data to the slow domain or receive datafrom the slow domain. In order to ensure that the synchronisation pulsesfrom the synchronisation outputs tx-sync and rx-sync can be successfullygenerated for the variable clock domains, then the synchronisationpulses are generated according to the following rules.

-   -   There is at least one cycle of the first (fast) clock signal        between transmit synchronisation pulses (tx-sync), and at least        one cycle of the first (fast) clock signal between receive        synchronisation pulses (rx-sync).    -   There is exactly one transmit synchronisation pulse (tx-sync)        per cycle of the second (slower) clock signal, and exactly one        receive synchronisation pulse (rx-sync) per cycle of the second        (slower) clock signal (the slow domain can only consume a single        set of data per cycle so there must only be a single tx clock        and it only produces a single set of data per cycle so there's        no point clocking the rx flops more often since it would just        waste power and the fast domain still needs to have an        indication of when the rx data has changed to new values).

An example timing diagram showing the generation of synchronisationpulses according to these rules is given in FIG. 4, in which the ratioof the second clock frequency to the first clock frequency is set to1:2. Another example of synchronisation pulses according to these rulesis given in FIG. 5, in which the ratio of the second clock frequency tothe first clock frequency is set to 2:5.

Note also, to maximise utility of the system, ideal synchronisationpulses preferably occur at the beginning and end of each slow clockcycle.

Generation of synchronisation pulses with real logic cells usuallyrequires some compromises on the set of divide ratios between the fastand slow domains (because with common clock frequencies and realisticgate delays, some of the ratios will violate timing constraints when thelogic is laid out). FIGS. 6 and 7 show circuit diagrams which work forall integer and half ratios between fast:slow domains (for example, 1:3,2:5, 2:6).

FIG. 6 shows synchronisation logic for generating the transmit pulsetx-sync. This comprises a first synchronisation flip-flop 22, a secondsynchronisation flip-flop 24, and an AND gate 26 with one inputinverted. The first and second synchronisation flip-flops 22 and 24 arerising edge triggered flip-flops with an inverter 25 and buffer 23 atthe clock input, so are in effect falling edge triggered flip-flops withslightly delayed clock inputs and will be considered as such for thepurpose of the following description. The signal input of the firstsynchronisation flip-flop 22 is connected to receive the second (slower)clock signal clk-B. The signal input of the second synchronisationflip-flop 24 is connected to the output of the first synchronisationflip-flop 22. The output of the first synchronisation flip-flop 22 isconnected to the non-inverted input of the AND gate 26. The output ofthe second synchronisation flip-flop 24 is connected to the invertedinput of the AND gate 26. The output of the AND gate 26 is arranged tosupply the transmit synchronisation pulses (tx-sync). The buffered andinverted clock inputs of the first and second synchronisation flip-flops22 and 24 are each connected to receive the first (faster) clock signalclk-A.

In operation, the second (slower) clock signal clk-B is shifted throughthe first and second synchronisation flip-flops 22 and 24 in dependenceon it being clocked by the first (faster) clock signal clk-A. The ANDgate 26 generates a transmit synchronisation pulse (tx-sync) wheneverthe value latched in the first synchronisation flip-flop 22 is logic-oneand the value latched in the second synchronisation flip-flop 24 islogic-zero. That is, whenever the slow clock signal clk-B was at alogic-low on the previous falling edge of the fast clock signal clk-Abut has changed to a logic-high since the most recent falling edge ofthe fast clock signal clk-A. This ensures the transmit synchronisationpulse (tx-sync) is generated according to the above rules. Refer also toFIGS. 4 and 5.

FIG. 7 shows synchronisation logic for generating the receive pulserx-sync. This comprises a third synchronisation flip-flop 28, a fourthsynchronisation flip-flop 30 with its signal input inverted, and an ANDgate 32 with both inputs inverted (i.e. a NOR gate). The third andfourth synchronisation flip-flops 28 and 30 are again rising edgetriggered flip-flops with an inverter 25 and buffer 23 at the clockinput, so are in effect falling edge triggered flip-flops with slightlydelayed clock inputs and will be considered as such for the purpose ofthe following description. The signal input of the third synchronisationflip-flop 28 is connected to receive the second (slower) clock signalclk-B. The inverted signal input of the fourth synchronisation flip-flop30 is connected to the output of the third synchronisation flip-flop 28.The output of the third synchronisation flip-flop 28 is connected to oneinput of the NOR gate 32. The output of the fourth synchronisationflip-flop 30 is connected to the other input of the NOR gate 32. Theoutput of the NOR gate 32 is arranged to supply the receivesynchronisation pulses (rx-sync). The buffered and inverted clock inputsof the third and fourth synchronisation flip-flops 28 and 30 are eachconnected to receive the first (faster) clock signal clk-A.

In operation, the second (slower) clock signal clk-B is shifted throughthe third and fourth synchronisation flip-flops 28 and 30 in dependenceon being clocked by the first (faster) clock signal clk-A. The secondclock signal clk-B is also inverted upon entry into the fourthsynchronisation flip-flop 30. The NOR gate 32 generates a receivesynchronisation pulse (rx-sync) whenever the value latched in both thethird and fourth synchronisation flip-flops 28 and 32 is logic-zero.That is, whenever the slow clock signal clk-B was at a logic-high on theprevious falling edge of the fast clock signal clk-A but has changed toa logic-low since the most recent falling edge of the fast clock signalclk-A. This ensures the receive synchronisation pulse (rx-sync) isgenerated according to the above rules. Again, refer also to FIGS. 4 and5.

As can be seen from the timings shown in FIG. 5, when a half-integerslow-to-fast clock frequency ratio is set between the dividers 6, thenthe overall effect of the generator of FIG. 6 is to generate the tx-syncpulses with a gap of one fast clock cycle therebetween except for everyalternate pulse where the gap is two clock cycles. Similarly, for ahalf-integer ratio, the overall effect of the generator of FIG. 7 is togenerate the rx-sync pulses with a gap of one fast clock cycletherebetween except for every alternate pulse where the gap is two clockcycles, with the rx-sync pulses being generated out of phase with thetx-sync pulses.

Note how the receive synchronisation pulses (rx-sync) and transmitsynchronisation pulses (tx-sync) are generated so as to ensure they arealways out of phase, and preferably mutually exclusive in time. Althoughthe link is preferably full duplex with the transmit and receive pathsbeing completely independent, there are still two reasons for generatingthe receive synchronisation pulses rx-sync out of phase with thetransmit synchronisation pulses tx-sync. The first is to ensure that thetx-sync pulse is early in the cycle and the rx-sync is late in thecycle. This allows the greatest possible time from a rising edge oftx-clk to a rising edge of the slow clock clk-B, and from a rising edgeof the slow clock cIk-B to a rising edge of rx-clk, which is preferableto cope with the timing of non-ideal logic (see the discussion inrelation to FIG. 12 below). The second and perhaps more important reasonis that the separation allows a cycle of turn around in the fastdomain—i.e. data can be gathered into the fast domain from a given cyclein the slow domain and the response sent in time to catch the followingcycle in the slow domain which is as fast as physically possible.

Note also, the reason that the synchronisation flip-flops 22, 24, 28 and30 are preferably rising edge triggered with an inverter and buffer atthe input (rather than simply using falling-edge triggered flip-flops)is because the two clock signals are generated with co-incident edgesand in the illustrated embodiments it is necessary to capture changes onthe slow clock on the same fast clock edge. That is, it is importantthat a rising edge on the fast clock captures the fact that a rising orfalling edge has coincidentally occurred on the slow clock.

As mentioned, generation of synchronisation pulses with real logic cellsusually requires some compromises on the set of divide ratios betweenthe fast and slow domains. This is because with common clock frequenciesand realistic gate delays, some of the ratios will violate timingconstraints when the logic is actually laid out in silicon. Moresophisticated schemes allow a greater range of divide ratios at theexpense of more logic. For example, a more sophisticated synchronisationgenerator 10 is now described in relation to FIG. 8, which supportsratios between the slow and fast clock frequencies including at least1:2, 1:2.25, 1:2.5, 1:2.75 and all ratios equal to or above 1:3 (i.e.where the frequency of the first clock signal is greater than or equalto three times the frequency of the second).

For generating the transmit synchronisation pulses, this synchronisationgenerator 10 comprises a first synchronisation flip-flop 38, a secondsynchronisation flip-flop 44 with its signal input inverted, and a firstAND gate 46. The first and second synchronisation flip-flops 38 and 44are each rising edge triggered flip-flops with an inverter 25 and buffer23 at the clock input, so are in effect falling edge triggeredflip-flops with slightly delayed clock inputs and will be considered assuch for the purpose of the following description. The signal input ofthe first synchronisation flip-flop 38 is connected to receive thesecond (slower) clock signal clk-B. The signal input of the secondsynchronisation flip-flop 44 is connected to the output of the firstsynchronisation flip-flop 38. The outputs of the first and secondsynchronisation flip-flops 38 and 44 are each connected to a respectiveinput of the first AND gate 46. The output of the first AND gate 46 isarranged to supply the transmit synchronisation pulses (tx-sync). Thebuffered and inverted clock inputs of the first and second flip-flops 38and 44 are each connected to receive the first (faster) clock signalclk-A.

To generate the transmit synchronisation pulses (tx-sync), the second(slower) clock signal clk-B is shifted through the first and secondsynchronisation flip-flops 38 and 44 in dependence on being clocked bythe first (faster) clock signal clk-A. The first AND gate 46 generates atransmit synchronisation pulse (tx-sync) whenever the value latched inthe first synchronisation flip-flop 38 is logic-one and the valuelatched in the second synchronisation flip-flop 44 is logic-one. Thatis, whenever the slow clock signal clk-B was at a logic-low on theprevious falling edge of the fast clock signal clk-A but has changed toa logic-high since the most recent falling edge of the fast clock signalclk-A. This ensures the transmit synchronisation pulses (tx-sync) aregenerated according to the above rules (at least one fast-cycle betweentransmit pulses and one and only one transmit pulse per slow-cycle).

The timing of the tx-sync pulses is shown in FIG. 9 for a ratio of1:2.25 (4:9) between the frequency of the second slower clock signalclk-B and the first faster clock signal clk-A. As can be seen, in thiscase the overall effect of the generator of FIG. 9 is to generate thetx-sync pulses with a gap of one fast clock cycle therebetween exceptfor every third pulse where the gap is two clock cycles.

To deal with a larger set of ratios between the frequency of the firstand second clock signals, the synchronisation generator 10 alsocomprises a comparison block 34 and a ratio indication flip-flop 36. Thecomparison block is connected to receive a signal indicative of thedivision ratio of the first (faster) clock divider 6 a (fast div ratio)and a signal indicative of the division ratio of the second (slower)clock divider 6 b divided by four (slow div ratio/4). The output of thecomparison block is connected to the signal input of the ratioindication flip-flop 36. The output of the ratio indication flip-flop 36is arranged to supply a ratio indication signal. The clock input of theratio indication flip-flop 36 is connected to receive the PLL sourceclock signal.

For generating the receive synchronisation pulses, in addition to thecomparison block 34 and the ratio indication flip-flop 36, thesynchronisation generator 10 further comprises: a third synchronisationflip-flop 40, a fourth synchronisation flip-flop 50, a fifthsynchronisation flip-flop 56, a second AND gate 42, a third AND gate 48,a fourth AND gate 54, and an OR gate 52. The third synchronisationflip-flop 40 is a rising edge triggered flip-flop with a buffer 23 atthe input. The fourth and fifth synchronisation flip-flops 50 and 56 arealso rising edge triggered flip-flops, but have an inverter 25 andbuffer 23 at the clock input, so are in effect falling edge triggeredflip-flops with slightly delayed clock inputs and will be considered assuch for the purpose of the following description. The signal input ofthe third synchronisation flip-flop is connected to receive the second(slower) clock signal clk-B. The second AND gate 42 is a three-input ANDgate with respective inputs connected to the output (i) of the firstsynchronisation flip-flop 38, the output (ii) of the thirdsynchronisation flip-flop 40, and the output of the ratio indicationflip-flop 36. The third AND gate 48 has one input connected to theoutput (iii) of the second AND gate 42. The output (iv) of the third ANDgate 48 is connected to the signal input of the fourth synchronisationflip-flop 50. The output (v) of the fourth synchronisation flip-flop 50is connected to an input of the OR gate 52. The other input of the ORgate 52 is connected to the output of the second AND gate 46. The output(vi) of the OR gate 52 is connected to the non-inverted input of thefourth AND gate 54 and to the other input of the third AND gate 48. Theinverted input of the fourth AND gate 54 is connected to the output ofthe second AND gate 42. The output (vii) of the fourth AND gate 54 isconnected to the signal input of the fifth synchronisation flip-flop 56.The buffered clock input of the third synchronisation flip-flop 40 isconnected to receive the first (faster) clock signal clk-A. The bufferedand inverted clock inputs of the fourth and fifth synchronisationflip-flops 50 and 56 are also connected to receive the first (faster)clock signal clk-A. The output of the fifth synchronisation flip-flop isarranged to supply the receive synchronisation pulses (rx-sync).

In operation, the comparison block 34 performs a comparison to determinewhether or not the division ratio of the first (faster) divider 6 a isless than or equal to a quarter of the division ratio of the second(slower) divider 6 b. The comparison block 34 outputs a ratio indicationsignal indicative of the result of this comparison, which is clockedinto to the ratio-indication flip-flop 36 in dependence on the PLLclock. So in this case, if the frequency of the first clock signal clk-Ais greater than or equal to four times the frequency of the second clocksignal clk-B, then the comparison block 34 outputs the ratio-indicationsignal at a logic-one. If not, it outputs the ratio-indication signal ata logic-zero.

If a logic-zero is held in the ratio indication flip-flop 36, toindicate the first clock frequency is less than four times the second,then the second AND gate 42 will be closed and will always output alogic-zero regardless of the bits held in the first synchronisationflip-flop 38 and third synchronisation flip-flop 40. This means theoutput of the third AND gate remains logic-zero, and so the input to theOR gate 52 from the third synchronisation flip-flop 50 also remains atlogic-zero. Therefore the output of the OR gate 52 is equal to its otherinput, i.e. the transmit synchronisation pulses (tx-sync). At the sametime, the inverted input of the fourth AND gate 54 is always alogic-one, making the fourth AND gate 54 transparent to the output ofthe OR gate 52. Thus the transmit synchronisation pulses (tx-sync) areprovided unchanged to the input of the fifth synchronisation flip-flop56, which delays them by one cycle of the first (faster) clock clk-A togenerates the receive synchronisation pulses (rx-sync).

The timing of the receive pulses (rx-sync) for a slow-to-fast frequencyratio of 4:9 is also shown in FIG. 9. Similarly to the tx-sync pulses,in this case the overall effect of the generator of FIG. 9 is togenerate the rx-sync pulses with a gap of one fast clock cycletherebetween except for every third pulse where the gap is two clockcycles. Again, note also that the receive synchronisation pulses(rx-sync) and transmit synchronisation pulses (tx-sync) are ensured tobe always out of phase, and preferably mutually exclusive in time.

If on the other hand a logic-one is held in the ratio indicationflip-flop 36 to indicate that the frequency of the first clock signalclk-A is greater than or equal to four times the frequency of the secondclock signal clk-B, then the receive pulses (rx-sync) are generated asdiscussed below.

The timing diagram of FIG. 10 a shows the timing of receive and transmitpulses for an example ratio of 2:8 (1:4) between the frequency of thesecond slower clock signal clk-B and the first faster clock signalclk-A. The timings of the signals marked (i) to (vii) in FIG. 10correspond to the signals at the points marked (i) to (vii) respectivelyin the circuit diagram of FIG. 8. FIG. 10 b shows the timing analternative ratio of 2:9 (1:4.5).

Again, the first AND gate 46 generates a transmit synchronisation pulse(tx-sync) whenever the value latched in the first synchronisationflip-flop 38 is logic-one and the value latched in the secondsynchronisation flip-flop 44 is logic-one. That is, whenever the slowclock signal clk-B was at a logic-low on the previous falling edge ofthe fast clock signal clk-A but has changed to a logic-high since themost recent falling edge of the fast clock signal clk-A. This ensuresthe transmit synchronisation pulses (tx-sync) are generated according tothe above rules (at least one fast-cycle between transmit pulses and oneand only one transmit pulse per slow-cycle).

As part of generating the receive synchronisation pulses (rx-sync), thesecond (slower) clock signal clk-B is clocked into the thirdsynchronisation flip-flop 40 in dependence on it being clocked by arising edge of the first (faster) clock signal clk-A. The second(slower) clock signal clk-B is also clocked into the firstsynchronisation flip-flop 38 in dependence on it being clocked by afalling edge of the first (faster) clock signal. This results in twosignals (i) and (ii) as shown in the examples of FIGS. 10 a and 10 b.

The third AND gate 48 takes the AND (iv) of this signal (iii) and theoutput (vi) of the OR gate 52. So (iv) must be low whenever (iii) islow, and must be high at least when both tx-sync and (iii) are high.This high is latched into the fourth synchronisation flip-flop 50 on afalling edge of clk-A. The value (v) in the fourth synchronisationflip-flop 50 remains latched high until the next falling edge of clk-Aafter (iii) goes low. So (iv) is high for the whole time while (iii) ishigh, and (v) is the signal (iv) shifted through the fourthsynchronisation flip-flop 50 in dependence on being clocked by a fallingedge of clk-A as shown in the examples of FIGS. 10 a and 10 b.

The output (vi) of the OR gate 52 is high whenever either tx-sync or (v)is high. The fourth AND gate 54 takes the AND (vii) of the output (vi)of the OR gate 52 and the opposite value to (iii) from the second ANDgate 42. So (vii) is high only when (vi) is high and (iii) is low. Thesignal (vii) is then clocked into the fifth synchronisation flip-flop 56in dependence on it being clocked by a falling edge of clk-A. Againthese signals are shown in the examples of FIGS. 10 a and 10 b.

The resulting receive synchronisation pulses (rx-sync) generated at theoutput of the fifth synchronisation flip-flop 56 are one fast clockcycle long and one fast clock cycle out of phase with the transmitsynchronisation pulses (tx-sync). The receive synchronisation pulses(rx-sync) are thus again also ensured to be generated according to theabove rules (at least one fast-cycle between transmit pulses and one andonly one transmit pulse per slow-cycle) and to be mutually exclusive intime to the transmit synchronisation pulses (tx-sync).

The extra logic in the sync-generator of FIG. 8 can be understood asfollows. The simpler sync generation logic of FIGS. 6 and 7 essentiallygenerates the tx-sync by detecting a rising edge on the slow clock andthe rx-sync by detecting a falling edge on the slow clock. The problemwith this is that for lots of the non-integer or non-half ratios wherethe ratio of fast:slow division factors is low (i.e. around 1:2 or 1:3)then the rx-sync pushes too late in the cycle causing the rx-clk tooccur after the slow clock edge. This means that changing data is caughtfrom the slow domain into the fast domain which hits metastabilityproblems or misses a cycle of data altogether. The tx-sync is alwaysgenerated as early as possible in the cycle, but cannot physically pushback into the previous cycle so does not display similar problems.

The more complicated logic of FIG. 8 solves this by changing themechanism for generating the rx-sync depending upon the ratio betweenthe fast and slow domains. So, when the ratio of fast:slow divisionfactors is <1:4 the rx-sync is generated directly from the tx-sync bydelaying it by a single cycle. This guarantees that the rx-sync cannever be too late because it is always guaranteed that the fast:slowratio is >=1:2 and the rx-sync is always within half a fast cycle (thetx-clk is within a whole cycle) of the beginning of the slow cycle, andit can be toleraterated for the rx-clock to be coincident with therising edge of the slow clock (but no later). This works alright becausethe slow domain can never be very fast (e.g. limited to 166 MHz inpreferred embodiments) so having the two sync pulses in successivecycles still actually allows quite a lot of time and the logic can buildwith real (non-ideal) gates.

When the fast domain is running at full speed, so the ratio between theclocks is high (i.e. >=1:4), then two successive cycles are a muchshorter time and it is necessary to push the rx-sync later in the slowcycle (ideally, as close to the end as possible but after the fallingedge on the slow clock is good enough). This is done by using theratio-4 control signal to switch back to the same mechanism as thesimpler version, which essentially generates the rx-sync from thefalling edge of the slow clock. The node marked (iii) in FIG. 8 can bethought of as a hold-off signal to delay the rx-sync pulse until after afalling edge on the slow clock.

The exact ratio for switching between the two mechanisms isn't a preciserequirement as long as its not set at too low a ratio. The ratio 1:4 isused in preferred embodiments because divide-by-four is trivial andrequires no extra gates (we simply shift the data right by 2 bits).

Note also that the simpler logic of FIGS. 6 and 7 can actually handlelarge ratios—and in fact quite a few ratios that don't immediately matchthe half/integer ratio rule stated. For both sets of circuits,generating a list of all the ratios that work is rather involved andvery dependent upon the qualities of the silicon process used to buildthe logic. Essentially, the faster the logic can run and the better thephysical layout (so there are tighter timing tolerances) the more ratioscan be supported by a given method of generating the sync signals.

Note that to allow the logic to be built from real (non-ideal) logicgates, it is preferable that:

-   -   the time from a rising edge of the transmit clock signal        (tx-clk) to the next rising edge of the second (slower) clock        signal clk-B is maximised,    -   the time from a rising edge of the second (slower) clock signal        clk-B to the next rising edge of the receive clock signal        (rx-clk) is maximised, and    -   the set-up and hold times

This preferred timing is illustrated in the timing diagrams of FIGS. 11and 12.

In a preferred application, the first circuit portion A in the fasterdomain comprises a processor and the second circuit portion B in theslower domain comprises one or more peripherals or peripheralinterfaces, preferably on the same chip. In this case, the first andsecond divider control signals (fast domain divider ctrl and slow domaindivider ctrl) are preferably generated by software executed on theprocessor, thus allowing software control of the frequencies of the twodomains. Peripherals typically operate at a much lower frequency than aprocessor, perhaps an order of magnitude lower.

It will be appreciated that the above embodiments are described only byway of example. In other embodiments for example, one or more additionaldividers 6 and synchronisation generators 10 could be provided in orderto scale to multiple clock domain boundary crossings. Further, anadditional gearbox with connections to domains A and B swapped aroundcould be provided to allow for the possibility that the second clockfrequency could be greater (faster) than the first clock frequency.Further, the transmit and receive clock gate cells 12 and 16 may bereplaced by re-circulating multiplexers. Further, the data transferredmay be any kind of information, control data or otherwise. The inventionmay be used in applications other than a soft modem and other than aprocessor and its peripherals. Other variations and uses of the presentinvention may be apparent to a person skilled in the art given thedisclosure herein. The scope of the invention is not limited by thedescribed embodiments, but only by the following claims.

1. A circuit comprising: clock circuitry comprising clock generatingmeans arranged to supply a first clock signal having a first fasterfrequency to a first circuit portion and a second clock signal having asecond slower frequency to a second circuit portion, the clockgenerating means being operable to vary the relative frequency of thefirst and second clock signals; synchronisation logic arranged togenerate pulses based on the first and second clock signals, each pulseindicating when to transfer data between the first circuit portion andthe second circuit portion; gating means arranged to produce a gatedclock signal by gating the first clock signal, the gating means beingopen when said pulses are asserted; and transfer means arranged to clockdata between the first circuit portion and the second circuit portionwhen clocked by the gated clock signal; wherein the clock circuitrycomprises control logic configured to generate a first control signal ata predetermined time in each cycle of the first clock signal prior to apredetermined edge of the first clock signal, and to generate a secondcontrol signal at a predetermined time in each cycle of the second clocksignal prior to a predetermined edge of the second clock signal, theclock generating means being configured such that a change in saidrelative frequency is conditional on a coincidence of the first andsecond control signals; and the synchronisation logic is configured togenerate said pulses such that there is at least one cycle of the firstclock signal between said pulses, and such that there is only one ofsaid pulses per cycle of the second clock signal.
 2. The circuitaccording to claim 1, wherein the clock generating means comprises: afirst clock divider operable to generate the first clock signal bydividing a source clock signal by a first variable factor; and a secondclock divider operable to generate the second clock signal by dividingthe source clock signal by a second variable factor; wherein each of thefirst and second clock dividers is configured such that a change in therespective first and second factors is conditional on a coincidence ofthe first and second control signals.
 3. The circuit according to claim1 or 2, wherein the synchronisation logic comprises a chain of at leasttwo flip-flops arranged to shift through the second clock signal whenclocked by the first clock signal, and combinational logic arranged togenerate said pulses in dependence on a combination of outputs from eachof said flip-flops.
 4. The circuit according to claim 3, wherein: theclock generating means is operable to select between a plurality ofpredetermined ratios between the first and second clock frequencies; andthe combinational logic is arranged to receive a ratio indication signalindicative of the ratio between the first and second frequencies, and togenerate said pulses using said ratio indication signal such that thereis at least one cycle of the first clock signal between said pulses andonly one of said pulses per cycle of the second clock signal regardlessof the selected ratio.
 5. The circuit according to claim 4, wherein atleast one of said predetermined ratios is less than four and at leastone of said predetermined ratios is greater than or equal to four; andthe ratio indication signal is indicative of whether or not the firstfrequency is greater than or equal to four times the second clockfrequency.
 6. The circuit according to claim 1, wherein the firstcircuit comprises a buffer arranged to buffer data to be transferred tothe second circuit.
 7. The circuit according to claim 1, wherein: thesynchronisation logic is arranged to generate transmit pulses whichindicate when to transmit data from the first circuit portion to thesecond circuit portion and receive pulses which indicate when to receivedata from the second circuit portion into the first circuit portion; thegating means comprises transmit gating means arranged to produce atransmit clock signal by gating the first clock signal, the transmitgating means being open when said transmit pulses are asserted, andreceive gating means arranged to produce a receive clock signal bygating the first clock signal, the receive gating means being open whensaid receive pulses are asserted; the transfer means is arranged totransmit data from the first circuit portion to the second circuitportion when clocked by the transmit clock signal, and to receive datafrom the second circuit portion into the first circuit portion whenclocked by the receive clock signal; and the synchronisation logic isconfigured to generate said transmit pulses based on the first andsecond clock signals such that there is at least one cycle of the firstclock signal between said transmit pulses and only one transmit pulseper cycle of the second clock signal, and to generate said receivepulses based on the first and second clock signals such that there is atleast one cycle of the first clock signal between said receive pulsesand only one receive pulse per cycle of the second clock signal.
 8. Thecircuit according to claim 7, wherein the synchronisation logic isconfigured to generate the receive pulses out of phase with the transmitpulses.
 9. The circuit according to claim 1, wherein the first circuitportion comprises a processor and the second circuit portion comprisesat least one peripheral device.
 10. The circuit according to claim 1,wherein the circuit is an integrated circuit.
 11. A method comprising:supplying a first clock signal having a first faster frequency to afirst circuit portion; supplying a second clock signal having a secondslower frequency to a second circuit portion; generating a first controlsignal at a predetermined time in each cycle of the first clock signalprior to a predetermined edge of the first clock signal; generating asecond control signal at a predetermined time in each cycle of thesecond clock signal prior to a predetermined edge of the second clocksignal; varying the relative frequency of the first and second clocksignals on the condition of detecting a coincidence of the first andsecond control signals; generating pulses based on the first and secondclock signals to indicate when to transfer data between the firstcircuit portion and the second circuit portion, such that there is atleast one cycle of the first clock signal between said pulses, and suchthat there is only one pulse per cycle of the second clock signal;producing a gated clock signal by gating the first clock signal so as topass it when said pulses are asserted; and transferring data between thefirst circuit portion and the second circuit portion, the transfer beingclocked by the gated clock signal.
 12. The method of claim 11,comprising: generating the first clock signal by dividing a source clocksignal by a first variable factor; and generating the second clocksignal by dividing the source clock signal by a second variable factor;wherein the generating of the first and second clock signals isperformed such that a change in the respective first and second factorsis conditional on a coincidence of the first and second control signals.13. The method of claim 11 or 12, the generating of said pulsescomprises shifting the second clock signal through a chain of at leasttwo flip-flops when clocked by the first clock signal, and generatingsaid pulses in dependence on a combination of outputs from each of saidflip-flops.
 14. The method of claim 13, wherein: the generating of theclock signals comprises selecting between a plurality of predeterminedratios between the first and second clock frequencies; and thegenerating of said pulses comprises using a ratio indication signalindicative of the ratio between the first and second frequencies, suchthat there is at least one cycle of the first clock signal between saidpulses and only one of said pulses per cycle of the second clock signalregardless of the selected ratio.
 15. The method of claim 14, wherein atleast one of said predetermined ratios is less than four and at leastone of said predetermined ratios is greater than or equal to four; andthe ratio indication signal is indicative of whether or not the firstfrequency is greater than or equal to four times the second clockfrequency.
 16. The method of claim 11, comprising buffering data to betransferred to the second circuit.
 17. The method of claim 11, wherein:the generating of said pulses comprises generating transmit pulses whichindicate when to transmit data from the first circuit portion to thesecond circuit portion and receive pulses which indicate when to receivedata from the second circuit portion into the first circuit portion saidgating comprises producing a transmit clock signal by gating the firstclock signal so as to pass it when said transmit pulses are asserted,and producing a receive clock signal by gating the first clock signal soas to pass it when said receive pulses are asserted; said transferringcomprises transmitting data from the first circuit portion to the secondcircuit portion, the transmission being clocked by the transmit clocksignal, and receiving data from the second circuit portion into thefirst circuit portion, the reception being clocked by the receive clocksignal; and the generating of said pulses comprises generating saidtransmit pulses based on the first and second clock signals such thatthere is at least one cycle of the first clock signal between saidtransmit pulses and only one of said transmit pulses per cycle of thesecond clock signal, and to generate said receive pulses based on thefirst and second clock signals such that there is at least one cycle ofthe first clock signal between said receive pulses and only one of saidreceive pulses per cycle of the second clock signal.
 18. The method ofclaim 17, wherein the receive pulses are generated out of phase with thetransmit pulses.
 19. The method of claim 11, wherein the first circuitportion comprises a processor and the second circuit portion comprisesat least one peripheral device.
 20. The method of claim 11, wherein thecircuit is an integrated circuit.
 21. A circuit comprising: clockcircuitry comprising clock generating means arranged to supply a firstclock signal having a first faster frequency to a first circuit portionand a second clock signal having a second slower frequency to a secondcircuit portion, the clock generating means being operable to selectbetween a plurality of predetermined ratios between the first and secondclock frequencies; synchronisation logic for generating pulses based onthe first and second clock signals, each pulse indicating when totransfer data between the first circuit portion and the second circuitportion; gating means arranged to produce a gated clock signal by gatingthe first clock signal, the gating means being open when said pulses areasserted; and transfer means arranged to transfer data between the firstcircuit portion and the second circuit portion when clocked by the gatedclock signal; wherein the synchronisation logic comprises a chain of atleast two flip-flops arranged to shift through the second clock signalwhen clocked by the first clock signal, and combinational logic arrangedto generate said pulses in dependence on a combination of outputs fromeach of said flip-flops; and the combinational logic is arranged toreceive a ratio indication signal indicative of the ratio between thefirst and second frequencies, and to generate said pulses using saidratio indication signal such that regardless of the selected ratio:there is at least one cycle of the first clock signal between saidpulses, and there is only one of said pulses per cycle of the secondclock signal.
 22. The circuit according to claim 21, wherein at leastone of said predetermined ratios is less than four and at least one ofsaid predetermined ratios is greater than or equal to four; and theratio indication signal is indicative of whether or not the firstfrequency is greater than or equal to four times the second clockfrequency.
 23. The circuit according to claim 21 or 22, wherein theclock circuitry comprises control logic configured to generate a firstcontrol signal at a predetermined time in each cycle of the first clocksignal prior to a predetermined edge of the first clock signal, and togenerate a second control signal at a predetermined time in each cycleof the second clock signal prior to a predetermined edge of the secondclock signal, the clock generating means being configured such that achange in said ratio is conditional on a coincidence of the first andsecond control signals.
 24. The circuit according to claim 21, whereinthe clock generating means comprises: a first clock divider operable togenerate the first clock signal by dividing a source clock signal by afirst variable factor; and a second clock divider operable to generatethe second clock signal by dividing the source clock signal by a secondvariable factor.
 25. The circuit according to claim 23, wherein each ofthe first and second clock dividers is configured such that a change inthe respective first and second factors is conditional on a coincidenceof the first and second control signals.
 26. The circuit according toclaim 21, wherein the first circuit comprises a buffer arranged tobuffer data to be transferred to the second circuit.
 27. The circuitaccording to claim 21, wherein: the synchronisation logic is arranged togenerate transmit pulses which indicate when to transmit data from thefirst circuit portion to the second circuit portion and receive pulseswhich indicate when to receive data from the second circuit portion intothe first circuit portion; the gating means comprises transmit gatingmeans arranged to produce a transmit clock signal by gating the firstclock signal, the transmit gating means being open when said transmitpulses are asserted, and receive gating means arranged to produce areceive clock signal by gating the first clock signal, the receivegating means being open when said receive pulses are asserted; thetransfer means is arranged to transmit data from the first circuitportion to the second circuit portion when clocked by the transmit clocksignal, and to receive data from the second circuit portion into thefirst circuit portion when clocked by the receive clock signal; and thesynchronisation logic is configured to generate said transmit pulsesbased on the first and second clock signals such that regardless of theselected ratio there is at least one cycle of the first clock signalbetween said transmit pulses and only one transmit pulse per cycle ofthe second clock signal, and to generate said receive pulses based onthe first and second clock signals such that regardless of the selectedratio there is at least one cycle of the first clock signal between saidreceive pulses and only one receive pulse per cycle of the second clocksignal.
 28. The circuit according to claim 27, wherein thesynchronisation logic is configured to generate the receive pulses outof phase with the transmit pulses.
 29. The circuit according to claim21, wherein the first circuit portion comprises a processor and thesecond circuit portion comprises at least one peripheral device.
 30. Thecircuit according to claim 21, wherein the circuit is an integratedcircuit.
 31. A method comprising: supplying a first clock signal havinga first faster frequency to a first circuit portion; supplying a secondclock signal having a second slower frequency to a 20 second circuitportion; selecting the relative frequency between the first and secondclock signals from a plurality of predetermined ratios; shifting thesecond clock signal through a chain of at least two flip-flops, theshifting being clocked by the first clock signal; receiving a ratioindication signal indicative of the ratio between the first and secondfrequencies; generating pulses which indicate when to transfer databetween the first circuit portion and the second circuit portion, byusing a combination of outputs from each of said flip-flops and saidratio indication signal such that, regardless of the selected ratio,there is at least one cycle of the first clock signal between saidpulses, and there is only one pulse per cycle of the second clocksignal; producing a gated clock signal by gating the first clock signalso as to pass it when the pulses are asserted; and transferring databetween the first circuit portion and the second circuit portion, thetransfer being clocked by gated clock signal.
 32. The method of claim31, wherein at least one of said predetermined ratios is less than fourand at least one of said predetermined ratios is greater than or equalto four; and the ratio indication signal is indicative of whether or notthe first frequency is greater than or equal to four times the secondclock frequency.
 33. The method of claim 31 or 12, comprising:generating a first control signal at a predetermined time in each cycleof the first clock signal prior to a predetermined edge of the firstclock signal; and generating a second control signal at a predeterminedtime in each cycle of the second clock signal prior to a predeterminededge of the second clock signal, generating the first and second clocksignals such that a change in said ratio is conditional on a coincidenceof the first and second control signals.
 34. The method according toclaim 31, comprising: generating the first clock signal by dividing asource clock signal by a first variable factor; and generating thesecond clock signal by dividing the source clock signal by a 25 secondvariable factor.
 35. The method according to claim 33, wherein a changein the respective first and second factors is conditional on acoincidence of the first and second control signals.
 36. The methodaccording to claim 31, comprising buffering data to be transferred tothe second circuit.
 37. The method of claim 31, wherein: the generatingof said pulses comprises generating transmit pulses which indicate whento transmit data from the first circuit portion to the second circuitportion and receive pulses which indicate when to receive data from thesecond circuit portion into the first circuit portion said gatingcomprises producing a transmit clock signal by gating the first clocksignal so as to pass it when said transmit pulses are asserted, andproducing a receive clock signal by gating the first clock signal so asto pass it when said receive pulses are asserted; said transferringcomprises transmitting data from the first circuit portion to the secondcircuit portion, the transmission being clocked by the transmit clocksignal, and receiving data from the second circuit portion into thefirst circuit portion, the reception being clocked by the receive clocksignal; and the generating of said pulses comprises generating saidtransmit pulses based on the first and second clock signals such thatregardless of the selected ratio there is at least one cycle of thefirst clock signal between said transmit pulses and only one of saidtransmit pulses per cycle of the second clock signal, and to generatesaid receive pulses based on the first and second clock signals suchthat regardless of the selected ratio there is at least one cycle of thefirst clock signal between said receive pulses and only one of saidreceive pulses per cycle of the second clock signal.
 38. The method ofclaim 37, wherein the receive pulses are generated out of phase with thetransmit pulses.
 39. The method of claim 31, wherein the first circuitportion 30 comprises a processor and the second circuit portioncomprises at least one peripheral device.
 40. The method of claim 31,wherein the circuit is an integrated circuit.